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11-1 product description ordering information typical applications features functional block diagram rf micro devices, inc. 7628 thorndike road greensboro, nc 27409, usa tel (336) 664 1233 fax (336) 664 0454 http://www.rfmd.com optimum technology matching? applied si bjt gaas mesfet gaas hbt si bi-cmos sige hbt si cmos ingap/hbt gan hemt sige bi-cmos gaas phemt prescaler 32/64 phase detector & charge pump lock detect loop flt 14 16 div ctrl dc bias 5 tx out 2 osc e 1 osc b 15 ld flt mod in 8 resntr+ 13 resntr- 12 3pd rf2516 vhf/uhf transmiiter ? 315/433mhz band systems ? local oscillator source ? part 15.231 applications ? remote keyless entry ? wireless security systems ? am/ask/ook transmitter the rf2516 is a monolithic integrated circuit intended for use as a low-cost am/ask tran smitter. the device is pro- vided in a 16-pin qsop-16 package and is designed to provide a phased locked frequency source for use in local oscillator or transmitter ap plications. the chip can be used in applications in the north american and european vhf/uhf bands. the integrated vco, phase detector, prescaler, and reference oscillator transistor require only the addition of an external crystal to provide a complete phase-locked loop. in addition to the standard power- down mode, the chip also includes an automatic lock- detect feature that disables the transmitter output when the pll is out-of-lock. ? fully integrated pll circuit ? integrated vco and reference oscillator ? 2.25v to 3.6v supply voltage ? low current and power down capability ? 100mhz to 500mhz frequency range ? out-of-lock inhibit circuit rf2516 vhf/uhf transmiiter rf2516pcba-410 fully assembled evaluation board 0 rev a17 060712 0.157 0.150 0.196 0.189 0.2440 0.2284 0.0688 0.0532 0.050 0.016 0.0098 0.0075 8 max 0min notes: 1. shaded lead is pin 1. 2. all dimensions are excluding mold flash. 3. lead coplanarity - 0.005 with respect to datum "a". 0.012 0.008 0.025 -a- 0.0098 0.0040 package style: ssop-16 9 rohs compliant & pb-free product
11-2 rf2516 rev a17 060712 absolute maximum ratings parameter rating unit supply voltage -0.5 to +3.6 v dc power down voltage (v pd ) -0.5 to v cc v mod in -0.5 to 1.1 v operating ambient temperature -40 to +85 c storage temperature -40 to +150 c parameter specification unit condition min. typ. max. overall t=25c, v cc =2.8v, freq=433mhz, r modin =3k frequency range 100 to 500 mhz modulation am/ask modulation frequency 1 mhz incidental fm 15 khz p-p output power +8.5 +10 dbm 50 load on/off ratio 75 db pll and prescaler prescaler divide ratio 32/64 vco gain, k vco 20 mhz/v frequency and board layout dependent. pll phase noise -97 dbc/hz 10khz offset, 50khz loop bandwidth -102 dbc/hz 100khz offset, 50khz loop bandwidth harmonics -60 dbc with output tuning. reference frequency 17 mhz crystal frequency spurs -50 dbc 50khz pll loop bandwidth max crystal r s tbd 35 50 for a typ. 1ms turn-on time. max crystal motional inductance 60 mh for a typ. 1ms turn-on time. charge pump current 100 ak pd =100 a/2 =0.0159ma/rad power down control power down ?on? v cc -0.3v v voltage supplied to the input; device is ?on? power down ?off? +0.3 v voltage supplied to the input; device is ?off? control input impedance 100k turn on time 1 2 ms crystal start-up, 13.57734mhz crystal. turn off time 1 2 ms power supply voltage 2.8 v specifications 2.25 3.6 v operating limits current consumption (avg.) 6 10.5 ma 50% duty cycle 10khz data applied to the mod in input. r modin (r10)=3k . output power/dc current consumption externally adjustable by modulation input resistor (see applicable application schematic). power down current 0 1 ua pd =0v, mod in=0v, div ctrl=0v caution! esd sensitive device. rf micro devices believes the furnished information is correct and accurate at the time of this printing. rohs marking based on eudirective2002/95/ec (at time of this printing). however, rf micro devices reserves the right to make changes to its products without notice. rf micro devices does not assume responsibility for the use of the described product(s).
11-3 rf2516 rev a17 060712 pin function description interface schematic 1osc b this pin is connected directly to the reference oscillator transistor base. the intended reference oscillator configuration is a modified colpitts. a 68pf capacitor should be connected between pin 1 and pin 2. 2osc e this pin is connected directly to th e emitter of the reference oscillator transistor. a 33pf capacitor should be connected from this pin to ground. see pin 1. 3pd power down control for all circuitry. when this pin is a logic ?low? all cir- cuits are turned off. when this pin is a logic ?high?, all circuits are oper- ating normally. a ?high? is v cc . diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 4gnd ground connection for the tx out amp. keep traces physically short and connect immediately to ground plane for best performance. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 5txout transmitter output. this output is an open collector and requires a pull- up inductor for bias/matching and a tapped capacitor for matching. 6gnd1 ground connection for the tx output buffer amplifier. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) pro- tection using the human body model. 7vcc1 this pin is used to supply bias to the tx buffer amplifier. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 8 mod in am analog or digital modulation can be imparted to the carrier by an input to this pin. an external resistor is used to bias the output amplifi- ers through this pin. the voltage at this pin must not exceed 1.1v. higher voltages may damage the device. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 9vcc2 this pin is used to supply dc bias to the vco, crystal oscillator, pre- scaler, phase detector, and charge pump. an if bypass capacitor should be connected directly to this pin and returned to ground. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. see pin 7. 10 gnd2 digital pll ground connection. diodes shown in the interface sche- matic provide 3kv electrostatic discharge (esd) protection using the human body model. osc e v cc osc b v cc pd tx ou t mod in rf in vcc1 v cc 1 k mod in tx ou t v cc gnd v cc
11-4 rf2516 rev a17 060712 pin function description interface schematic 11 vref p bias voltage reference pin for bypassing. the bypass capacitor should be of appropriate size to provide filtering of the reference crystal fre- quency and be connected directly to this pin. diodes shown in the inter- face schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 12 resntr- the resntr pins are used to supply dc voltage to the vco, as well as to tune the center frequency of the vco. equal value inductors should be connected to this pin and pin 13. 13 resntr+ see pin 12. 14 loop flt output of the charge pump. an rc network from this pin to ground is used to establish the pll bandwidth. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 15 ld flt this pin is used to set the threshol d of the lock-detect circuit. a shunt capacitor should be used to set an rc time constant with the on-chip series 1k resistor. this signal is used to clamp (enable or disable) the mod in circuitry. the time constant should be approximately 10 times the reference period. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 16 div ctrl logic ?high? input selects divide-by-64 prescaler. logic ?low? input selects divide-by-32 prescaler. diodes shown in the interface sche- matic provide 3kv electrostatic di scharge (esd) protection using the human body model. vref p v cc resntr- resntr+ loop flt 4 k loop fl t v cc v cc ld flt 1 k v cc div ctrl
11-5 rf2516 rev a17 060712 rf2516 theory of operation introduction short range radio devices are becoming commonplace in today?s environment. the most common examples are the remote keyless entry systems popular on many new cars and trucks, and the ubiquitous garage door opener. other applications are emerging with the growth in home security , automation and the advent of various remote control applica- tions. typically these devices have been simplex, or one-way, links. they are also typically built using surface acoustic wave (saw) devices as the frequency control elements. this approach has been attractive because the saw devices have been readily available and a transmitter, for example, could be built with only a few additional components. recently however, rf micro devices, inc. (rfmd), has introduced several new components that enable a new class of short- range radio devices based on the use of crystals and phase-locked loops for frequency control. these devices are supe- rior in performance and comparable in cost to the traditional saw-based designs. the rf2516 is an example of such a device. the rf2516 is targeted for applications such as 315mhz and 433mhz band remote keyless entry systems and wireless security systems, as well as other remote control applications. the rf2516 transmitter the rf2516 is a low-cost am /ask vhf/uhf transmitter designed for applicatio ns operating within the frequency range of 100mhz to 500mhz. in particular, it is intended for 315mhz to 433mhz band systems, remote keyless entry systems, and fcc part 15.231 periodic transmitte rs. it can also be used as a local osc illator signal source. the integrated vco, phase detector, presca ler, and reference oscillator requir e only the addition of an extern al crystal to provide a complete phase-locked loop. in addition to the standard power-down mode, the chip also includes an automatic lock-detect feature that disables the transmitter out put when the pll is out-of-lock. the device is manufactured on a 25gh z silicon bipolar-cmos process and packag ed in an industry standard ssop-16 plastic package. this, combined with the low external parts count, enables the designer to achieve small-footprint, high- performance, low-cost designs. the rf2516 is designed to operate from a supply voltag e ranging from 2.25v to 3.6v, accommodating designs using three nicd battery cells, two aaa flashlight cells, or a lithium button battery. the device is capable of pr oviding up to +10dbm output power into a 50 load, and is intended to comply with fcc requirements for unlicensed remote control transmitters. esd protection is provided on all pins except vco and tx out. while this device is intended for ook operation, it is possible to use narrowband fm. this is accomplished by modulat- ing the reference oscillator rather than applying the data to th e mod in input pin. the mod in pin should be tied high to cause the device to transmit. the deviation will be set by pulling limits of the crystal. deviation su fficient for the transmis - sion of voice and other low data rate signals can therefore be accomplished. refer to the application schematic in the data sheet for details. the rf2516 functional blocks a pll consists of a reference oscillator, a phase detector, a loop filter, a voltage controlled oscillator (vco), and a pro- grammable divider in the feedback path. the rf2516 includes all of these internally, except for the loop filter and the ref- erence oscillator?s crystal an d two feedback capacitors. the reference oscillator is a colpitts type osc illator. pins 1 (osc b) and 2 (osc e) provide connections to a transistor that is used as the refe rence oscillator. the colpitts conf iguration is a low parts count topo logy with reliable performance and reasonable phase noise. alternatively, an external signal could be injected into the base of the transistor. the drive level should, in either case, be around 500mv pp . this level prevents overdriving the device and keeps the phase noise and reference spurs to a minimum. the prescaler divides the vco frequency by either 64 or 32, using a series of flip-flops, depending upon the logic level present at the div ctrl pin. a high logic level will se lect the 64 divisor. a low logic le vel will select the 32 divisor. this divided signal is then fed into the phase detector where it is compared with the reference frequency.
11-6 rf2516 rev a17 060712 the rf2516 contains an onboard phase detector and charge pump. the phase detector compares the phase of the ref- erence oscillator to the phase of the vco. the phase detector is implemented using flip-flops in a topology referred to as either ?digital phase/frequency detector? or ?digital tri-stat e comparator?. the circuit consists of two d flip-flops whose outputs are combined with a nand gate which is then tied to the reset on each flip-flop. the outputs of the flip-flops are also connected to the charge pump. each flip-flop output sign al is a series of pulses whose frequency is related to the flip-flop input frequency. when both inputs of the flip-flops are identical, the signal s are both frequency- and phase-locked. if they are different, they will provide signals to the charge pump which will either char ge or discharge the loop f ilter, or enter into a high impedance state. the name ?tri-sta te comparator? comes from this. the main benefit of this type of detector is the ability to correct for errors in both phase and frequency. when locked, the detector uses phase error for correction. when unlocked, it uses frequency error for correction. this type of detector will lock under a ll conditions. the charge pump consists of two transistors, one for charging the loop filter and the other for discharging the loop filter. its inputs are the outputs of the phase detector flip-flops. since there are two flip-flops, there are four possible states. if both amplifier inputs are low, then the amplifier pair goes into a high impedance state, maintaining the charge on the loop filter. the state where both inpu ts are high will not occur. the other states are either charging or discharging the loop fil- ter. the loop filter integrates the pulses coming from the charge pump to create a control voltage for the voltage con- trolled oscillator. the vco is a tuned differential amplifier with the bases and collectors cross-coupled to provide positive feedback and a 360 phase shift. the tuned circuit is located in the collectors, and is comprised of internal varactors and external induc- tors. the designer selects the inductors for the desired frequency of operation. these inductors also provide dc bias for the vco. the output of the vco is buffered and applied to the prescaler circuit, where it is divided by either 32 or 64, as selected by the designer, and compared to the reference oscillator frequency. the transmit amplifier is a two-stage amplifier consisting of a driver and an open collector final stage. it is capable of providing 10dbm of output power into a 50 load while operating from a 3.6v power supply. the lock-detect circuitry connects to the output of the phase detector circuitry and is used to disable the transmitter when the vco is not phase-locked to the re ference oscillator. this is necessary to avoid unwanted ou t-of-band transmis- sion and to provide compliance with regulatory limits during an unlocked condition. there are many possible reasons for the pll not to be locked. for instance, there is a short period during the start of any vco in which the vco begins os cillating and the refer ence oscillator builds up to full ampl itude. during this period, the frequency will likely be outside t he authorized band. typically, the vco starts much faster than the refere nce oscillator. once both vco and refe rence oscillators are running, the phase detector can start slew ing the vco to the correct fre- quency, slowly sliding across 200mhz of occupied spectrum. in competitive devices, the vco radiates at full power under all of these conditions. the lock protection circuit in the rf2516 is intended to stab ilize quickly after power is applie d to the chip, and to disable the base drive to the transmit amplifier. th is attenuates the outp ut to levels that will be gene rally acceptable to regulatory boards as spurious emissions. once the phase detector has locked the oscillators, then the lock circuit enables the mod in pin for transmission of the desired data. there is no need for an external microprocessor to monitor the lock status, although that can be done with a low current a/d converter in a system micro, if needed. the lock-detect circuitry con- tains an internal resistor which, combined with a designer-chosen capacitor for a particular rc time constant, filters the lock-detect signal. this signal is then passed through an internal schmitt trigger and used to enable or disable the trans- mit amplifier. if the oscillator unlocks, even momentarily, the protection circ uit quickly disables the output until the lock is stable. these unlocks can be caused by low battery voltage, poor power supply regulation, severe shock of the crystal or vco, antenna loading, component failure, or a myriad of unexpected single-point failures.
11-7 rf2516 rev a17 060712 the rf2516 contains onboard band gap reference voltage circuitry which provides a stable dc bias over varying tem- perature and supply voltages. additionally, the device features a power-down mode, eliminating battery disconnect switches. designing with the rf2516 the reference oscillator is built around the onboard transistor at pins 1 and 2. the intended topology is that of a colpitts oscillator. the colpitts oscilla tor is quite common and requir es few external components, making it ideal for low-cost solutions. the topology of th is type of oscillato r is as seen in th e following figure. this type of oscillator is a pa rallel resonant circuit for a fundam ental mode crystal. the transistor amplif ier is an emitter follower and the voltage gain is developed by the tapped capacitor impedance transformer. the series combination of c 1 and c 2 act in parallel with the input capacitance of the transistor to capacitively load the crystal. the nominal capacitor values can be calculated with the following equations 6 : and the load capacitance is usually 32pf. the variable freq is the oscillator frequency in mhz. the frequency can be adjusted by either changing c 2 or by placing a variable capacitor in series with the crystal. as an example, assume a desired frequency of 14mhz and a load capacitance of 32pf. c 1 =137.1pf and c 2 =41.7pf. these capacitor values pr ovide a starting point. the drive level of the oscillator should be checked by looking at the sig- nal at pin 2 (osc e). it has been found that the level at this pin should generally be around 500mv pp or less. this will reduce the reference spur levels and reduce noise from distortion. if this level is higher than 500mv pp then increase the value of c 1 . the values of these capacitors are usually tweaked during design to meet performance goals, such as mini- mizing the start-up time. additionally, by placing a variable capacitor in series with the crystal, one is able to adjust the frequency. this will also alter the drive level, so it should be checked again. an important part of the overall design is the voltage controlled oscillator . the vco is configured as a differential amplifier. the vco is tuned via internal varactors. the varactors are tuned by the loop filter output voltage through a 4k resistor. x1 c2 c1 v cc c 1 60 c load ? freq mhz ----------------------- - = c 2 1 1 c load ------------- 1 c 1 ------ ? -------------------------- =
11-8 rf2516 rev a17 060712 as mentioned earlier, the inductors and the varactors are tuni ng a differential amplifier. to tune the vco the designer only needs to calculate the value of the inductors connected to pins 12 and 13 (resntr- and resntr+). the inductor value is determined by the equation: in this equation, f is the desired operating frequency and l is the value of the inductor required. the value c is the amount of capacitance presented by the varactors and parasitics. for calculation purposes 1.5pf should be used. the factor of one-half is due to the inductors being in each leg. as an example, assume an operating frequency of 433mhz. the calculated value of each inductor is 45nh. a 47nh inductor would be appropriate as the closest available value. the setup of the vco can be summarized as follows. first, open the loop. next, get the vco to run on the desired fre- quency by selecting the proper inductor and capacitor values. the capac itor value will need to include the varactor and circuit parasitics. after the vco is running at the desired frequency, set the vco sensitivity. the sensitivity is determined by connecting the control voltage input point to ground and noting the frequency. connect the same point to the supply, and again note the frequency. the difference between these two frequencies divided by the supply voltage is the vco sensitivity expressed in hz/v. increasing the inductor value while decreasing the capacitor value will increase the sensitivity. decreasing the inductor value while increasing the capacitor value will lower the sensitivity. when increasing or decreasing component values, make sure that the center frequency remains constant. finally, close the loop. external to the part, the designer needs to implement a loop filter to complete the pll. the lo op filter converts the out- put of the charge pump into a voltage that is used to co ntrol the vco. internally, the vco is connected to the charge pump output through a 4k resistor. the loop filter is then connected in parallel to this point at pin 14 (loop flt). this limits the loop filter topology to a second order filter usually consisting of a shunt capacitor and a shunt series rc. a pas- sive filter is most common, as it is a low-cost and low-noise design. an additional pole could be used for reducing the ref- erence spurs, however there is not a way to add the series resistor. however, this should not be a reason for concern. 4 k loop flt l l resntr+ resntr- l 1 2 f ?? ---------------- ?? ?? 2 1 c --- - 1 2 -- - ?? =
11-9 rf2516 rev a17 060712 the schematic of the loop filter is: the transfer function is: where the time constants are defined as: and the frequency at which unity gain occurs is given by: this is also the loop bandwidth. if the phase margin (pm) and the loop bandwidth ( lbw ) are known, it is possible to calculate the time constants. these are found using the equations 4 : and 4 k loop flt l l resntr+ resntr- fs () r 2 s 2 1 + ? s 2 s 1 1 ) + ? ( ?? ------------------------------------------- ? = 2 r 2 c 2 ? = 1 r 2 c 1 c 2 ? c 1 c 2 + ------------------- ? ? ? ? ? = lbw 1 1 2 ? ------------------ - = 1 pm () sec pm () tan ? lbw -------------------------------------------------- = 2 1 lbw 2 1 ? ----------------------- - =
11-10 rf2516 rev a17 060712 with these known, it is then possible to determine the values of the filter components. 4 as an example, consider a loop bandwidth of 50khz, a phase margin of 45, a divide ratio of 64, a k vco of 20mhz/v, and a kpd of 100 a/2 rad. time constant 1 is 1.31848 s, time constant 2 is 7.68468 s, c 1 is 20.9pf, c 2 is 100.8pf, and r 2 is 76.2k . in order to perform these calculations, one will need to know the value of two constants, k vco and k pd . k pd is calculated by dividing the charge pump current by 2 . for the rf2516, the charge pump current is 100 a. k vco is best found empirically as it will change with freque ncy and board parasitics. by briefly conn ecting pin 14 (loop flt) to vcc and then to ground, the frequency tuning range of the vco can be seen. dividing the difference between these two frequen- cies by the difference in the voltage gives k vco in mhz/v. the control lines provide an interface for connecting the device to a microcontroller or other signal generating mecha- nism. the designer can treat pin 8 (mod in), pin 16 (div ct rl), and pin 3 (pd) as control pins whose voltage level can be set. the lock-detect voltage at pin 15 (ld flt) is an output that can be monitored by the microcontroller. pin 15 (ld flt) is used to set the threshold of the lock-detect circuit . a shunt capacitor is used to set an rc time con- stant with an on-chip series 1k resistor. the time constant should be approximately 10 times the reference period. general rf bypassing techniques must be observed to get the best performance. choose capacitors such that they are series resonant near the frequency of operation. board layout is always an area in which great care must be taken. the board material and thickness are used in calcu- lating the rf line widths. the use of vias for connection to the ground plane allows one to connect to ground as close as possible to ground pins. when laying out the traces around the vco, it is desirable to keep the parasitics equal between the two legs. this will allow equa l valued inductor s to be used. pre-compliance testing should be performed during the design process. this can be done with a gtem cell or at a compliance testing laboratory. it is recommended that pre-compliance testing be performed so that there are no sur- prises during final compliance testing. this will help keep the product development and release on schedule. working with a laboratory offers the benef it of years of compliance testing experi ence and familiarity with the regulatory issues. also, the laboratory can often provide feedback that w ill help the designer make the product compliant. on the other hand, having a gtem cell or an open air test site loca lly offers the designer th e ability to rapidly determine whether or not design changes impact the product's compliance. set-up of an open air test site and the associated cali- bration is not trivial. an altern ative is to use a gtem test cell. after the design has been comple ted and passes compliance test ing, application will need to be made with the respec- tive regulatory bodies for the geograph ic region in which the product will be op erated to obtain fi nal certifications. c 1 1 2 ---- - k pd k vco ? lbw 2 n ? ----------------------------- 1 lbw 2 ? () 2 + 1 lbw 1 ? () 2 + ---------------------------------------- ?? = c 2 c 1 2 1 ---- - 1 ? ?? ?? ? = r 2 2 c 2 ------ =
11-11 rf2516 rev a17 060712 rf2516 typical applications fcc part 15.231 periodic transmitter - 315mhz automotive keyless entry transmitter the following information is taken or paraphrased from the code of federal regulations title 47, part 15, section 231 (47 cfr 15.231). part 15 discusses radio frequency devices and section 231 discusses periodic transmissions. please refer to the regulation itself as the final authority. additional information may be found on the internet at www.fcc.gov. to highlight the main guidelines outlined by this section, there are five main limitations: operating frequency, transmission content, transmission duration, emission bandwidth, and spurious emissions. part 15.231 allows operation in two bands: 40.66mhz to 40.70mhz and above 70mhz. transmission is limited to control signals such as alarm systems, door openers, remote switches, etc. radio control of toys is not permitted, nor is contin- uous transmission such as voice or video. data transmission other than a recognition code is not permitted. transmis- sion time is limited to 5 seconds (paragraph a) or for 1 second with greater than ten seconds off (paragraph e). emission bandwidth between 70mhz and 900mhz can not be more than 0.25% of the center frequency. above 900mhz, the emission bandwidth cannot be greater than 0.50% of the center frequency. the emission bandwidth is determined from the points that are 20db down from the modulated carrier. this corresponds to an occupied bandwidth of 4.5mhz at a center frequency of 902mhz, 1.1mhz at 433mhz, and 788khz at 315mhz. spurious emissions limits are listed in tabular form for various frequency ranges in the section 231. above 470mhz with a manually activated transmitter, the fundamental fiel d strength at a distance of 3 meters shall not exceed 12,500microvolts/meter. the spurious emissions shall not ex ceed 1,250microvolt/meter at a distance of 3meters above 470mhz. refer to appendix a for a method of converting field strength to power. in the frequency range of 260mhz to 470mhz, one needs to linearly interpolate the maximum emissions level for both the fundamental and spurious emissions. the equation for this line is given by: this equation is derived from the endpoints of the frequency range and their respective field strengths. note that the field strength is in microvolts per meter and the frequency is in megahertz. to determine the spurious level, divide the level calculated above for the spurious frequency by ten. as an example, assume the fundamental is 315mhz and the reference frequency is 9.8mhz. the field strengths of the fundamental, the reference spurs, and the harmonics of the fundamental up through the tenth harmonic are calculated in the following table the occupied bandwidth limit is 787.5khz. as shown in table a, the fifth, seventh, and ninth harmon- ics fall into restricted bands as called out in section 15.205. the limits for these restricted bands are called out in section 15.209. the power level in the last column is the level if the output is connected directly to a spectrum analyzer. refer to appendix a as to how this column was calculated. local oscillator source since the rf2516 has a phase-locked vco, it can be used as a signal source. the device is an ask/ook transmitter, with the data provided at the mod in pin. when the mod in is a high logic level, the carrier is transmitted. when mod in is a low logic level, then the carrier is not transmitted. therefore, to use the rf2516 as signal source, simply tie the mod in pin to the supply voltage, through a suitable series resistor (minimum 3k ). e v m ------- 41 2 3 -- - freq mhz 7083 1 3 -- - ? ? =
11-12 rf2516 rev a17 060712 conclusions the rf2516 is an am/ook vhf/uhf transmitter that features a phase-locked output. this device is suitable for use in a cfr part 15.231 compliant product as we ll as a local oscillator signal source. two examples showing these applications were discussed. the rf2516 is packaged in a low-cost plastic package and requires few external parts, thus making it suitable for low- cost designs. table a frequency (mhz) 15.205 limits ( v/m@3m) 15.231 limits ( v/m@3m) final fcc mask ( v/m@3m) final fcc mask ( v/m@3m) power level (dbm, 50 ) ref spur 305.2 - 604.17 604.17 55.62 -39.61 1 315.0 - 6041.67 6041.67 75.62 -19.61 ref spur 324.8 - 604.17 604.17 55.62 -39.61 2 630.0 - 604.17 604.17 55.62 -39.61 3 945.0 - 604.17 604.17 55.62 -39.61 4 1260.0 - 604.17 604.17 55.62 -39.61 5 1575.0 500 - 500.00 53.98 -41.25 6 1890.0 - 604.17 604.17 55.62 -39.61 7 2205.0 500 - 500.00 53.98 -41.25 8 2520.0 - 604.17 604.17 55.62 -39.61 9 2835.0 500 - 500.00 53.98 -41.25 10 3150.0 - 604.17 604.17 55.62 -39.61
11-13 rf2516 rev a17 060712 pin out 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 div ctr l ld flt loop fl t resntr + resntr - vrefp gnd2 vcc2 osc b osc e pd gnd tx out gnd1 vcc1 mod in
11-14 rf2516 rev a17 060712 application schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 9.83 mhz 33pf *not populated on standard evaluation board. osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 56 nh 16 k j1 tx out 220 pf 10 tx vcc 100 pf mod in s1 cas-120b 10 82 nh 82 nh 2 k 10 nf 4.3 k 2.2 nf 1 nf v c c v c c v c c pd
11-15 rf2516 rev a17 060712 application schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 9.83 mhz 33pf osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 56 nh 16 k j1 tx out 220 pf 10 tx vcc 100 pf s1 cas-120b 10 82 nh 82 nh 2 k 10 nf 4.3 k 2.2 nf 1 nf pd d1 smv1249-011 150 k audio v cc v cc rf2516 audio transmitter v cc v cc
11-16 rf2516 rev a17 060712 application schematic 433mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 13.57734 mhz pwr dwn 4.3 k 220 pf 220 pf 10 nf 220 pf div ctr 10 nf tx out 33pf 1 nf 2.2 nf 39 nh 2 k 10 10 nf *not populated on standard evaluation board. * 2.8 v cc (v) mod. in res. value (r5) i cc (ma) p out (dbm) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k 17.38 10.51 8.68 7.82 7.18 6.75 6.45 6.18 5.99 5.80 5.66 7.45 8.78 7.23 6.00 4.73 3.81 2.98 2.30 1.63 1.00 0.35 2.0 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k i cc (ma) 11.08 10.83 4.61 4.00 3.63 3.42 3.26 3.15 3.07 3.01 2.95 p out (dbm) -6.23 -4.40 -5.61 -6.66 -8.08 -8.93 -10.04 -10.71 -11.58 -12.32 -13.10 2.4 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k i cc (ma) 14.05 9.00 7.48 6.73 6.16 5.79 5.53 5.29 5.13 4.98 4.86 p out (dbm) 7.94 7.63 5.95 4.64 3.35 2.40 1.47 0.75 0.05 -0.60 -1.26 3.2 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k p out (dbm) 6.77 9.70 8.30 7.11 5.91 5.02 4.16 3.51 2.89 2.26 1.66 i cc (ma) 20.90 12.12 9.66 8.95 8.23 7.75 7.42 7.10 6.89 6.68 6.52 3.6 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k p out (dbm) 5.78 10.42 9.18 8.08 6.88 6.02 5.19 4.52 3.93 3.35 2.72 i cc (ma) 24.68 13.88 10.94 10.14 9.34 8.81 8.44 8.09 7.86 7.63 7.44 osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 68 nh 2 pf 50 strip 15 pf 10 nh 15 pf 10 nh 22 nh 220 pf 10 nf 220 pf 10 nf 10 3 k 10 nf mod in 39 nh v cc v cc v cc pd
11-17 rf2516 rev a17 060712 evaluation board schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 c8 68 pf y1 9.83 mhz c7 33pf *not populated on standard evaluation board. osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip c6 4 pf 50 strip l3 56 nh r4 16 k j1 tx out c5 220 pf tx vcc c4 100 pf mod in s1 cas-120b r2 10 l2 82 nh l1 82 nh r1 2 k c1 1 f r3 4.3 k c2 2.2 nf c3 1 nf vcc vcc vcc gnd p1-1 vcc1 p1-3 mod in p1 1 2 3 con3 b1 lith batt vcc + - 2516400, rev a pd r5 10
11-18 rf2516 rev a17 060712 evaluation board schematic 433mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 c2 68 pf x1 13.57734 mhz pwr dwn r2 4.3k c7 220 pf c9 220 pf c10 10 nf vcc c12 220 pf div ctrl c11 10 nf c1 33pf c6 1 nf c8 2.2 nf l2 39 nh r4 2k r3 10 c13 10 nf *not populated on standard evaluation board. c17* osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip c3 4 pf 50 strip l4 68 nh c15 2 pf 50 strip c14 15 pf l3 10 nh c16 15 pf l5 10 nh l6 22 nh c18 220 pf c19 10 nf vcc c5 220 pf c4 10 nf r1 10 vcc r5 3k c20 10 nf l1 39 nh j1 tx out j2 mod in p1 1 2 3 con3 vcc nc gnd p2 1 2 3 con3 div ctrl gnd pwr dwn pd
11-19 rf2516 rev a17 060712 evaluation board layout (315mhz) board size 1.285? x 1.018? board thickness 0.062?, board material fr-4
11-20 rf2516 rev a17 060712 evaluation board layout (433mhz) board size 1.392? x 0.813? board thickness 0.062?, board material fr-4
11-21 rf2516 rev a17 060712 433mhz phase noise 0 1.0 1.0 -1.0 10.0 1 0 . 0 - 1 0 . 0 5.0 5 . 0 - 5 . 0 2.0 2 . 0 - 2 . 0 3.0 3 . 0 - 3 . 0 4.0 4 . 0 - 4 . 0 0.2 0 . 2 - 0 . 2 0.4 0 . 4 - 0 . 4 0.6 0 . 6 - 0 . 6 0.8 0 . 8 - 0 . 8 rf2516 output z swp max 1ghz swp min 0.1ghz vcc = 3 v vcc = 2 v vcc = 3.3 v 1.0 ghz 0.1 ghz
11-22 rf2516 rev a17 060712

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